法国专利FR3055505A1 LIGHTING CIRCUIT AND VEHICLE HEADLIGHT

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专利摘要:
A lighting circuit (400) controls a light source (310) having a plurality of light emitting elements (312_1; 312_N) and includes a bypass switch circuit (450) having a plurality of bypass switches (452_1; 452_N) connected in parallel with the plurality of light emitting elements, a boost converter (410) which amplifies a supply voltage to produce a DC voltage (VDC) stabilized at a variable target voltage, a step-down converter (430) which receives the DC voltage to provide a target current stabilized drive current (IREF) to the light source and which includes a hysteresis controller (480) for stabilizing the drive current (ILAMP) between a maximum value and a value and to modify a difference between the maximum value and the minimum value so that a switching frequency of the down converter tends to a value constant, and a voltage control circuit (460) which is adapted to dynamically change the target voltage of the upconverter as a function of an output voltage of the down converter.
公开号:FR3055505A1
申请号:FR1757880
申请日:2017-08-25
公开日:2018-03-02
发明作者:Takao Muramatsu；Satoshi Kikuchi
申请人:Koito Manufacturing Co Ltd；
IPC主号:

专利说明:

TECHNICAL FIELD The present invention relates to a headlight intended for an automobile or the like.
BACKGROUND OF THE INVENTION A vehicle headlight can generally be switched between a low beam and a high beam. The low beam allows the predetermined lighting of a nearby area and provides a light distribution intended not to cause the glare of an oncoming vehicle or of a preceding vehicle. The low beam is mainly used when driving in urban areas. The main beam, on the other hand, provides intense lighting over a large area at the front over a long distance. The main beam is mainly used when driving at high speed on a road with few oncoming or previous vehicles. Therefore, although the high beam provides the driver with better visibility than the low beam, the high beam would cause the driver of a previous vehicle or a pedestrian in front of the vehicle to dazzle (see par example, document JP-A-2015-153657).
In recent years, the technique of the adaptive driving beam (ADB) has been proposed which dynamically and adaptively regulates a distribution curve of the light intensities as a function of vehicle conditions. The ADB technique reduces the glare of a vehicle or a pedestrian by detecting the presence of a preceding vehicle, an oncoming vehicle or a pedestrian at the front of the vehicle and by reducing the light in an area corresponding to the vehicle or pedestrian detected.
A vehicle headlight with an ADB function is described below. Figures IA and IB are block diagrams of vehicle headlights with the ADB function according to a comparative technique. Comparative technique should not be recognized as a state of the art.
Referring to Figure IA, an IR vehicle headlight includes a light source 2 and a lighting circuit 20R. An ADB beam high beam lighting zone is divided into N sub-zones (N is a natural number greater than or equal to 2). The light source 2 comprises a plurality of light emitting elements 3_1 to 3_N respectively corresponding to the N sub-areas. Each light emitting element 3 is a semiconductor device such as a light emitting diode (LED) or a laser diode (DL), and is arranged to illuminate the corresponding sub-area.
The lighting circuit 20R receives a supply voltage Vbat from a battery 4 and modifies a light distribution of the high beam by individually controlling the on state (ignition) and the blocked state (extinction) of each of the light emitting elements 3_1 to 3_N. In addition, the lighting circuit 20R adjusts an effective luminance by regulating an Ilamp current flowing in the light emitting element 3 by pulse width modulation (PWM). high frequency.
The lighting circuit 20R comprises a step-up converter 22, a bypass switch circuit 24 and a light distribution control device 26. The step-down converter 22 is a constant current converter which produces a current of Ilamp output stabilized at a target value Iref to be supplied to the light source 2.
The bypass switch circuit 24 includes a plurality of bypass switches 28_1 to 28_N corresponding to the plurality of light emitting elements 3_1 to 3_N. Each bypass switch 28_i is mounted in parallel with the corresponding light emitting element 3. When the bypass switch 28_i is in the off state, the driving current Ilamp flows in the corresponding light emitting element 3_i, so that the light emitting element 3_i lights up. When the bypass switch 28_i is in the on state, the driving current Ilamp flows through the bypass switch 28_i, so that the corresponding light emitting element 3_i turns off. The light distribution control device 26 controls the on / off state of the plurality of bypass switches 28_1 to 28_N, based on a distribution curve of the light intensities. In addition, the light distribution control device 26 individually controls the plurality of bypass switches 28_1 to 28_N by PWM modulation to achieve a dimming of the light intensity by PWM modulation of the plurality of light emitting elements 3_1 to 3_N. On the assumption that the driving current Ilamp flows in M light emitting elements among the plurality of light emitting elements 3_1 to 3_N (0 <M <N), a voltage between the two ends of the light source 2, namely an output voltage Vqut of the step-up converter 22, is equal to M x Vf. For a better understanding, a direct voltage Vf of the light emitting element 3 is assumed here to be uniform. Consequently, the output voltage Vout of the step-up converter 22 varies over time as a function of the combination of on and off states of the plurality of bypass switches 28_1 to 28_N.
As described above, the step-up converter 22 can be considered as a constant current source which produces the constant driving current Ilamp · It should be noted that the step-up converter 22 does not actively modify the output voltage Vout · The output voltage Vout varies due to the dynamic variation of the combined impedance of the light source 2 and the bypass switch circuit 24, namely the load impedance of the step-up converter - step-down 22.
Referring to Figure IB, a lighting circuit 20S includes a step-up converter 30 and a step-down converter32 mounted in series, in place of the step-up converter step-down 22 of Figure 1 A. When Vf = 5 V and that N = 12, the voltage between the two ends of the light source 2 varies dynamically from 0 to 60 V. The step-up converter 30 is a constant-voltage converter which stabilizes a direct output current Vdc at a voltage level higher than the maximum value of 60 V of the voltage between the two ends of the light source 2. The step-down converter 32 has a constant current output similar to that of the step-up converter step-down 22 of FIG. IA and stabilizes the current Ilamp of the light source 2 to a predetermined target value.
After examining the lighting circuit 20S in FIG. 1B, the inventors have identified the following problems. Specifically, as soon as the dimming frequency by PWM modulation effected by the bypass switch circuit 24 is several hundred Hz, the load impedance of the step-down converter 32 also varies at a frequency of several hundred Hz. 'To obtain a reactivity of such high speed, it is necessary to carry out a regulation by hysteresis (regulation by all or nothing) in the step-down converter 32. Figure 2 is a block diagram of the step-down converter 32 provided with the regulation by hysteresis.
The step-down converter 32 includes an output circuit 40 and a hysteresis regulator 50. The output circuit 40 includes an input capacitor Ci, a switching transistor Mi, a rectifier diode Di, a choke coil Li and a current detection resistance Rcs In hysteresis regulation, an upper current limit Iupper and a lower current limit Ibottom are defined near a target value Iref of the driving current Ilamp which is a object of regulation. The switching transistor goes into the off state when the drive current Ilamp (coil current II) reaches the upper limit of current Iupper, and the switching transistor goes to the on state when the drive current Ilamp drops at the lower Ibottom current limit, and this cycle repeats. The hysteresis regulator 50 comprises a current detection circuit 52, a hysteresis comparator 54, and a driving circuit 56. The current detection resistance Rcs is placed on a path of the driving current Ilamp · A voltage drop proportional to the driving current Ilamp is generated between the two ends of the current detection resistor Rcs · The current detection circuit 52 produces a current detection signal Vcs corresponding to the voltage drop of the resistor current detection Rcs · The hysteresis comparator 54 compares the current detection signal Vcs with an upper threshold Vthh corresponding to the upper current limit Iupper and with a lower threshold Vthl corresponding to the lower current limit Ibottom and produces a pulse Scnt command line corresponding to the comparison results. The driving circuit 56 drives the switching transistor Mi as a function of the control pulse Scnt · [0018] FIG. 3 is a diagram of functional waveforms of the step-down converter 32 of FIG. 2. In a section where the control pulse Scnt is at a passing level (for example, a high level), the switching transistor Mi is in the conducting state, and in a section where the control pulse Scnt is at blocked level (for example , a low level), the switching transistor Mi is in the off state. When the switching transistor is in the conducting state, a voltage between the two ends of the inductor Li is equal to Vin ~ Vout · Consequently, the coil current II flowing in the inductor Li (at know the attack current Ilamp) rises according to a slope of (Vin ~ Vout) / Li. When the switching transistor Mi is in the off state, a voltage between the two ends of the inductor Li is -Vout · Consequently, the coil current II (namely the driving current Ilamp) drops according to a slope equal to Vout / Li.
The conduction time Ton and the blocking time Toff of the switching transistor Mi are given by equations (1) and (2).
T _O n = AI / {(V, n-Vout) / L ₁ } ... (1)
T off = ΔΙ / (V ουτ / Li) - (2)
ΔΙ is a hysteresis width (ripple width) of the coil current II, i.e. the difference between a maximum value Iupper and a minimum value Ibottom · ΔΙ is proportional to the difference Δν between the upper threshold signal thh and the lower threshold signal Vthl, as shown in the following equation.
ΔΙ = AV / Rcs In the vehicle headlight 1S in FIG. 1B, although an input voltage Vin (Vdc) of the step-down converter 32 remains constant, the output voltage Vout fluctuates dynamically with the control by PWM modulation of the bypass switch circuit 24. The switching period Ton + Toff of the switching transistor Mi, namely the switching frequency f _S w, fluctuates with the output voltage Vout, which makes it difficult to cope with noise electromagnetic.
SUMMARY The present invention has been designed taking into account the above circumstances and one aspect of the present invention relates to a vehicle headlight capable of suppressing a frequency fluctuation of the switching converter.
One aspect of the present invention relates to a lighting circuit designed to control a light source comprising a plurality of light emitting elements connected in series. The lighting circuit includes a bypass switch circuit, a step-up converter, a step-down converter and a voltage adjustment circuit. The bypass switch circuit includes a plurality of bypass switches, each of which is mounted in parallel with a corresponding light emitting element of the plurality of light emitting elements. The step-up converter is designed to amplify a supply voltage to produce a stabilized DC voltage at a variable target voltage. The step-down converter is designed to receive DC voltage to provide a stabilized drive current to a target current at the light source. The down converter has a hysteresis regulator according to a hysteresis regulation method. The hysteresis regulator is designed to stabilize the drive current between a maximum value and a minimum value which are defined near the target current and to modify a difference between the maximum value and the minimum value so that a switching frequency of the buck converter tends to a constant value. The voltage adjustment circuit is designed to dynamically modify the target voltage of the step-up converter, depending on an output voltage of the step-down converter.
According to the above configuration, the output voltage of the step-down converter can follow a charge variation at high speed by using hysteresis regulation. Furthermore, as soon as the switching frequency can be stabilized by adjusting the difference between the maximum value and the minimum value, the noise characteristics can be eliminated.
When the input voltage of the step-down converter remains constant and the switching frequency is stabilized, the difference between the input voltage and the output voltage of the step-down converter can become significant. In this case, in order to reduce the coil current and thus reduce a fluctuation width (ripple width) of the driving current, it is necessary to select a component having a high inductance and therefore a large component, as an inductor (coil). Regarding this problem, the difference between the input voltage and the output voltage of the step-down converter can be reduced, the ripple width compared to the same inductance value can therefore be reduced and it is possible to select accordingly. a small inductor in the above configuration.
The voltage adjustment circuit can be designed to modify the target voltage so that a difference between the target voltage of the step-up converter and the output voltage of the step-down converter does not exceed a predetermined value or tends towards it.
Therefore, the voltage between the two ends of the inductor of the step-down converter can be kept at a predetermined value, and the size of the inductor can be reduced by reducing the predetermined value.
The voltage adjustment circuit can be designed to modify the target voltage more quickly when the output voltage of the step-down converter is raised than when the output voltage of the step-down converter drops. Thus, it is possible to prevent the control of the buck converter from being unstable.
The voltage adjustment circuit can be designed to modify the target voltage in a shorter time than a control period of the bypass switch circuit, when the output voltage of the step-down converter rises. Thus, the insufficiency of the output voltage (the voltage between the two ends of the light source) of the step-down converter, and the decrease in luminance of the light source can be eliminated.
The voltage regulation circuit can be designed to modify the target voltage in less than half the control period of the bypass switch circuit, when the output voltage of the step-down converter rises.
The voltage adjustment circuit can be designed to modify the target voltage in a time longer than the control period of the bypass switch circuit, when the output voltage of the step-down converter drops. Thus, the oscillation of the buck converter can be eliminated.
The voltage adjustment circuit can be designed to modify the target voltage in a time greater than three times the control period of the bypass switch circuit, when the output voltage of the step-down converter drops.
The voltage adjustment circuit includes a peak hold circuit which is designed to receive an output detection voltage corresponding to the output voltage of the step-down converter. The output voltage can correspond to the output voltage of the peak hold circuit. Therefore, the target voltage can be adjusted by a simple analog circuit.
The voltage adjustment circuit comprises a diode which is designed to receive an output detection voltage corresponding to the output voltage of the step-down converter at an anode thereof, a first resistor which is placed between a cathode of the diode and a ground, a capacitor which has one end connected to ground, and a second resistor which is placed between the other end of the capacitor and the cathode of the diode. The target voltage can be set according to the voltage of the capacitor.
The voltage adjustment circuit includes an A / D converter which is designed to convert the output detection voltage corresponding to the output voltage of the step-down converter into a digital value, a peak detection circuit which is designed to producing a peak detection signal representing a peak of the numerical value, a filter which is adapted to receive the peak detection signal and which has faster reactivity in an upward direction and slower reactivity in a downward direction , and a D / A converter which is designed to convert an output signal of the filter into an analog voltage. The voltage adjustment circuit can set the target voltage according to the analog voltage.
The lighting circuit may further include a light distribution control device which is designed to control the plurality of bypass switches according to a desired curve of distribution of light intensities. The voltage setting circuit may be designed to regulate the target voltage based on a voltage between the two ends of the light source, estimated from the on / off states of the plurality of bypass switches. The response delay can be eliminated by regulation with anticipatory action, based on the estimated value of the voltage between the two ends of the light source.
The lighting circuit can be designed to control a plurality of light sources and include a plurality of step-down converters corresponding to the plurality of light sources. The voltage setting circuit can be configured to change the target voltage based on the highest of the output voltages of the plurality of step-down converters. Thus, a step-up converter can be shared by the plurality of step-down converters, and the circuit scale can be reduced.
Another aspect of the present invention relates to a vehicle headlight. The vehicle headlight comprises a light source comprising a plurality of light emitting elements connected in series and the lighting circuits described above, intended to control the light source.
Any combination of the above building blocks and the building blocks and substitute expressions in methods, apparatus, systems or the like are also effective as aspects of the present invention.
According to one aspect of the present invention, it is possible to suppress the frequency fluctuation of the switching converter.
BRIEF DESCRIPTION OF THE DRAWINGS The above and other aspects of the present invention will become more apparent and be better appreciated from the following description of illustrative embodiments of the present invention, read in conjunction with the drawings annexed, among which:
Figures IA and IB are block diagrams of a vehicle headlight with an ADB function according to a comparative technique;
FIG. 2 is a block diagram of a step-down converter provided with hysteresis regulation;
Figure 3 is a diagram of functional waveforms of the step-down converter of Figure 2;
FIG. 4 is a block diagram of a vehicle headlight comprising a lighting circuit according to one embodiment;
FIG. 5 is a block diagram showing an example of a specific configuration of the lighting circuit;
Figures 6A and 6B are block diagrams showing examples of configuration of a frequency stabilization circuit;
Figure 7 is a waveform diagram showing basic operation of the lighting circuit;
Figure 8 is a diagram of functional waveforms when the lighting circuit of Figure 4 performs dimming by PWM modulation;
Figures 9A and 9B are diagrams illustrating other advantages of the lighting circuit;
Figures 10A and 10B are block diagrams showing examples of configuration of a voltage adjustment circuit;
FIGS. 11A and 11B are diagrams of functional waveforms of the lighting circuit, when a distribution curve of the light intensities is modified;
FIG. 12 is a functional diagram of a voltage adjustment circuit according to a first modification; and Figures 13A and 13B are block diagrams of a lighting circuit according to a second modification.
DETAILED DESCRIPTION [0039] Embodiments of the present invention are described below with reference to the drawings. Identical or equivalent components, elements and processes shown in each drawing have the same reference numbers, and where appropriate, repetitive descriptions are omitted. The embodiments are not intended to limit the scope of the present invention, but are merely illustrative and all of the features described in the embodiments and their combinations are not essential to the present invention.
In the description, "a state where an element A is connected to an element B" includes not only a case where the element A and the element B are physically and directly connected, but also a case where the element A and element B are indirectly connected via other elements which have no significant effects on an electrical connection state or which do not alter functions or effects due to their connection .
Similarly, "a state where an element C is placed between an element A and an element B" includes not only a case where the element A and the element C, or the element B and the element C are directly connected, but also a case where element A and element C, or element B and element C are indirectly connected via other elements which have no significant effects on their electrical connection or which do not alter any functions or effects due to their connection.
For better understanding, a vertical axis and a horizontal axis of waveform diagram or timing diagram referenced in this specification are enlarged and reduced appropriately, and each waveform is also simplified, exaggerated or highlighting.
In the description, the reference numerals assigned to electrical signals such as voltage signals or current signals, or circuit elements such as resistors and capacitors represent voltage values and values of current or resistance values and capacitance values.
Figure 4 is a block diagram of vehicle headlight 300 having a lighting circuit 400 according to one embodiment. The vehicle headlight 300 configures a headlight system 200 together with a battery 202 and a vehicle electronic control unit (ECU) 204. The battery 202 provides a battery voltage (supply voltage) Vbat of 12 V or 24 V. The lighting circuit 400 receives the battery voltage Vbat as a power supply to switch on a light source 310. The lighting circuit 400 is connected to the vehicle ECU 204 via a bus 206 such as CAN (from the English “Controller Area Network”) and LIN (from the English “Local Interconnect Network”). Vehicle headlight 300 has an ADB function and dynamically changes a light intensity distribution curve based on information or a command value from vehicle ECU 204.
The vehicle headlight 300 comprises a light source 310 and the lighting circuit 400. The light source 310 comprises a plurality of (N) light emitting elements 312_1 to 312_N connected in series. Light emitting elements 312 are semiconductor light emitting devices, such as a light emitting diode (LED), a laser diode (DL), and organic light emitting diode (EL) that emit light of corresponding luminance at an Ilamp drive current · The number of N light-emitting elements 312 corresponds to a resolution in the regulation of the light intensity distribution curve. The number N is for example equal to 4, 8, 12, 24, without this being limiting.
The lighting circuit 400 is connected to the light source 310 by means of a bundle of electric wires 320. The lighting circuit 400 comprises a step-up converter 410, a step-down converter 430, a bypass switch circuit 450, a voltage adjustment circuit 460 and a light distribution control device 470. The bypass switch circuit 450 includes a plurality of bypass switches 452_1 to 452_N, and the i-th bypass switch 452_i is mounted in parallel with its corresponding light emitting element 312_i among the plurality of light emitting elements 312_1 to 312_N. In FIG. 4, the number of bypass switches 452 is equal to the number of light emitting elements 312, without this being limiting.
The light distribution control device 470 controls the plurality of bypass switches 452_1 to 452_N of the bypass switch circuit 450, so as to obtain a desired curve of distribution of the light intensities, on the basis of information or a control instruction coming from the vehicle ECU 204. On the assumption that a direct voltage Vf of the light emitting elements 312 is equal to 5 V and that N = 12, the output voltage Vout can vary from 0 at 60 V.
The step-up converter 410 includes an adjustment terminal (ADJ) and amplifies the supply voltage Vbat to produce a direct voltage Vdc which is stabilized at a target voltage Vdc (ref) corresponding to a voltage Vadj of the terminal ADJ. In other words, the step-up converter 410 stabilizes the DC voltage Vdc at the target voltage Vdc (ref) which is proportional to the voltage Vadj of the terminal ADJ.
In one example, the output voltage Vdc of the step-up converter 410 is divided by resistors R31 and R32 and fed back to the input. The step-up converter 410 sets a switching duty cycle, so that the feedback signal divided into voltage Vfb agrees with the voltage Vadj of the terminal ADJ.
In steady state, when the conditions Ki = Vadj / Vout and K ₂ = V _D c / Vadj are satisfied,
Vdc = Ku x K ₂ x V _0UT .
Here, Ki x K ₂ is called “control gain G”. If G = Ki x K ₂ > 1, Vdc can be maintained at a voltage level higher than Vout and the potential difference AV between an input voltage and an output voltage of the step-down converter 430 can satisfy Vdc Vout = (Κι x K ₂ - 1) x Vout- Here, the potential difference AV designates the difference between a maximum value of the output voltage Vout and the input voltage. If the maximum value of the output voltage Vout is equal to 60 V, and Ki x K ₂ = 1.1, the potential difference AV between the input voltage and the output voltage can be less than 0.1 x 60 = 6 V. The difference in AV potential is preferably in the range of about 1 to IV.
The step-down converter 430 receives the DC voltage V _D c and supplies the stabilized driving current Ilamp at the target current Iref, to the light source 310. As described below, the step-down converter 430 includes a hysteresis regulator 480 according to a hysteresis regulation method. The hysteresis regulator 480 stabilizes the driving current Ilamp between a maximum value Iupper and a minimum value Ibottom which are defined close to the target current Iref · Furthermore, the hysteresis regulator 480 modifies the difference AI between the maximum value Iupper and the minimum value Ibottom, so that the switching frequency f _S w of the down converter 430 tends towards a constant value.
The voltage adjustment circuit 460 dynamically modifies the voltage Vadj of the terminal ADJ of the step-up converter 410 as a function of the output voltage Vout of the step-down converter 430, namely the voltage between the two ends of the light source 310.
Preferably, the voltage adjustment circuit 460 modifies the voltage Vadj of the terminal ADJ, so that the difference between the target voltage V _D c (ref) and the output voltage V _D c of the step-up converter 410 and the output voltage Vout of the step-down converter 430 (in other words, the difference between the input voltage and the output voltage of the step-down converter 430) does not exceed a predetermined value or tends towards it. For example, the voltage regulation circuit 460 can modify the voltage Vadj of the terminal ADJ according to the peak of the output voltage Vout of the step-down converter 430. For example, the voltage regulation circuit 460 can also produce the voltage Vadj based on the peak of the output voltage (output detection voltage) Vouts divided by the resistors & u and R ₄₂ .
Figure 5 is a block diagram showing an example of a specific configuration of the lighting circuit 400. The step-up converter 410 comprises an output circuit 412 and a control device 414. The output circuit 412 comprises a coil d inductance L ₂ , a switching transistor M ₂ , a diode D ₂ , and a capacitor C ₂ . The voltage Vadj of the terminal ADJ is applied to a reference pin REF of the control device 414. A feedback voltage Vfb corresponding to the output voltage Vdc of the step-up converter 410 is fed back to a feedback pin FB of the control device 414 The control device 414 drives the switching transistor M ₂ so that the feedback voltage Vfb agrees with the reference voltage Vadj · The control device 414 can use a commercially available integrated circuit whose configuration is not not particularly limited.
The step-down converter 430 includes an output circuit 432 and the hysteresis regulator 480. The configuration of the output circuit 432 is similar to that of FIG. 1. When a current detection signal Vcs reaches an upper threshold Vthh corresponding to the maximum value Iupper of the driving current Ilamp, the hysteresis regulator 480 blocks the switching transistor Mi, when the current detection signal Vcs reaches a lower threshold Vthl corresponding to the minimum value Ibottom of the driving current Ilamp , the hysteresis regulator 480 turns on the switching transistor Mj and the hysteresis regulator 480 performs the above operation repeatedly.
As described above, the hysteresis regulator 480 stabilizes the switching frequency fsw by adjusting the difference between the upper threshold Vthh and the lower threshold Vthl- The hysteresis regulator 480 comprises a voltage source 482, a comparator 484, a driving circuit 486 and a frequency stabilization circuit 488. The voltage source 482 is a variable voltage source which produces the upper threshold Vthh and the lower threshold V _T hl · The average value of upper threshold Vthh and lower threshold Vthl corresponds to the target value I _RE f of the driving current Ilamp · When the control pulse S _C nt, as an output of comparator 484, is at a passing level ( during a period when the switching transistor Mi is in the conducting state), the comparator 484 compares the current detection signal Vcs with the upper threshold Vthh · When the control pulse Scnt is at a blocked level ( during a period when the tran switching transistor Mi is in the blocked state), the comparator 484 compares the current detection signal Vcs with the lower threshold Vthl · The driving circuit 486 drives the switching transistor Mi as a function of the control pulse Scnt · The frequency stabilization circuit 488 adjusts the potential difference (hysteresis width) AVhys between the upper threshold Vthh and the lower threshold Vthl so that the switching frequency fsw of the switching transistor Mj agrees with a frequency target Îref · In particular, when the switching frequency fsw is greater than the target frequency f _RE F, the hysteresis width AVhys is increased so as to decrease the switching frequency fsw · When the switching frequency fsw is lower than the target frequency îref, the hysteresis width AVhys is reduced so as to increase the switching frequency fsw · Figures 6A and 6B are block diagrams representing the examples of specific configuration of the frequency stabilization circuit 488. The frequency stabilization circuit 488 comprises a frequency detection circuit 490 and an error amplifier 492. The frequency detection circuit 490 receives the control pulse Scnt or a signal having the same frequency as the control pulse Scnt and produces a frequency detection signal Vfreq representing the switching frequency f _S w- The error amplifier 492 amplifies the error between the frequency detection signal Vfreq and a reference signal Vfreq (ref) which represents the target value of the switching frequency.
The voltage source 482 produces the upper threshold Vthh and the lower threshold Vthl as a function of an error signal V _E rr. For example, the voltage source 482 includes resistors R _H , Rl and a current source 494. The current source 494 delivers a current Ierr corresponding to the error signal Verr. An analog voltage Vadim is applied to one end of the resistor R _H and Vthh is produced at the other end of the resistor R _H where Vthh = Vadim ^_ Ierr x Rh · One end of the resistor R _L is connected to ground, and V _T hl is produced at the other end of the resistance Rl where Vthl = Ierr x Rl · If Rh = Rl = R, the mean value of Vthh and Vthl is Vadim / 2. Consequently, the average value of the coil current I _L , namely the luminance of the light source 310, can be subject to a gradation as a function of the voltage Vadim · In addition, the difference (hysteresis width AVhys ) between Vthh and Vthl satisfies AVhys = 2 x Ierr x R.
The specific configuration example of the voltage source 482 is illustrated in Figure 6B. The current source 494 comprises an operational amplifier OA51, a transistor M51 and a resistor R _L. In this configuration, Vthl = Verr and I _E rr = V _E rr / Rl [0064] Apart from the examples illustrated in FIGS. 6A and 6B, those skilled in the art can design the frequency stabilization circuit 488 or the 482 voltage source with equivalent functions which are included within the scope of the invention.
The configuration of the lighting circuit 400 is as described above. A description is then given of the operation of the lighting circuit 400. FIG. 7 is a diagram of waveforms representing a basic operation of the lighting circuit 400. For a more concise explanation and a better understanding, the operation is shown when the number of bypass switches 452 which are in the on state decreases over time, without dimming by PWM modulation in the bypass switch circuit 450. In this case, the output voltage Vout rises over time. The voltage adjustment circuit 460 increases the voltage Vadj of the terminal ADJ as a function of the rise in the output voltage Vout · Consequently, the input voltage Vin (Vdc) of the step-down converter 430 follows the rise in the output voltage Vout · To simplify the explanation, it is assumed here that the difference AV between the input voltage and the output voltage remains constant.
A description is then given of the operation of the step-down converter 430. When the potential difference AV between the input voltage and the output voltage is substantially constant, an upward slope (Vin ^- Vout) / Li of the coil current I _L (Ilamp lamp current) is substantially constant. On the other hand, a downward slope -Vout / Li becomes steep as the output voltage Vout rises. The step-down converter 430 modifies the difference AIhys between the upper current limit Iupper and the lower current limit Ibottom, so that the switching frequency f _S w (period: 1 / fsw) becomes constant.
More specifically, the frequency stabilization circuit 488 of the step-down converter 430 adjusts the difference AIhys between the upper threshold Vthh and the lower threshold Vthl, so that the switching frequency fsw becomes constant. The hysteresis width AVhys increases as the output voltage Vout rises.
The basic operation of the lighting circuit 400 is as described above. Figure 8 is a diagram of functional waveforms when the lighting circuit 400 of Figure 4 performs dimming by PWM modulation. When the light intensity distribution curve is constant, each bypass switch 452 of the bypass switch circuit 450 is repeatedly controlled according to the same model, and the output voltage Vout of the step-down converter 430 repeats the same waveform at during the PWM Tpwm modulation period · A PWM Tpwm modulation period is a few milliseconds, especially around 3 to 5 ms.
In this example, the output voltage Vout varies from 15 to 40 V during the PWM modulation period Tpwm · The voltage adjustment circuit 460 produces the voltage Vadj corresponding to the peak of the output voltage Vout, namely 40 V, and supplies it to the ADJ terminal. When the control gain G is equal to 1.1, the output voltage Vdc of the step-up converter 410 is stabilized at 44 V, and the potential difference AV between the input voltage and the output voltage of the step-down converter 430 is of 4 V.
The operation of the lighting circuit 400 is as described above. A description is then given of the advantages of the lighting circuit 400.
According to the lighting circuit 400, as soon as the step-down converter 430 uses hysteresis regulation, the output voltage Vout of the step-down converter 430 can follow a charge variation at high speed. In addition, since it is possible to stabilize the switching frequency fsw by adjusting the difference AIhys between the maximum value Iupper and the minimum value Ibottom of the driving current Ilamp, the noise characteristics can be eliminated.
FIGS. 9A and 9B are diagrams illustrating other advantages of the lighting circuit 400. FIG. 9A represents the coil current I _L of the lighting circuit 400 of FIG. 4, and FIG. 9B represents the coil current II when the output Vdc of the step-down converter 430 is constant. For example, Vout = 20 V and Vdc = 22 V in Figure 9A, and V _O ut = 20 V and V _D c = 60 V in Figure 9B. When comparing FIG. 9A to FIG. 9B, FIG. 9B has the same downward slopes as in FIG. 9A, but a steeper upward slope than in FIG. 9A. In this case, on the assumption that the inductance values Li of the step-down converters are the same, the ripple width of the coil current II in FIG. 9B is greater to obtain the same switching frequency fsw desired. In particular, when a frequency stabilization command is used, a ripple width becomes even greater, as the output voltage Vout rises. Therefore, in order to maintain the ripple width within the allowable range, while maintaining the DC voltage Vdc at 60 V and within an output voltage range Vout, it is necessary to increase the inductance value Li significantly and it is therefore necessary to select, as an inductance coil Li, an expensive and large component.
In this regard, according to the lighting circuit 400, the potential difference between the input voltage and the output voltage of the step-down converter 430 can be eliminated by the voltage adjustment circuit 460. Consequently, it is it is possible to select a low inductance value Li and a small dimension, even when the frequency stabilization command is used in the step-down converter 430. Furthermore, it is possible to reduce the cost of the device, since the components to be low inductance values are generally inexpensive.
In particular, the voltage adjustment circuit 460 modifies the voltage Vadj of the terminal ADJ, so that the difference AV between the target voltage Vdc (ref) of the step-up converter 410 and the output voltage V _O ut of the converter step 430 does not exceed or tend towards a predetermined value. In addition, it is possible to reduce the size of the inductor by decreasing this predetermined value.
A description is then given of the command when the light intensity distribution curve is changed dynamically. When the light intensity distribution curve is constant, the output voltage Vout varies during a PWM modulation period, but the peak of the output voltage V _O ut is constant. On the other hand, the peak value of the output voltage V _O ut varies when the light intensity distribution curve changes.
The voltage adjustment circuit 460 changes the voltage Vadj of the terminal ADJ more quickly when the output voltage Vout of the step-down converter is raised 430 than when the output voltage Vout falls · The rise and the fall here designate those falling within the time scale at least equal to the MLI modulation period and greater than the MLIL modulation period. More precisely, the voltage Vadj of the terminal ADJ preferably varies in a shorter time than the control period (PWM modulation period) T _PWM of the bypass switch circuit 450, during the rise in the output voltage Vout of the step-down converter 430. For example, the voltage Vadj of the terminal ADJ follows the output voltage Vout within a time scale less than half the PWM modulation period T _P wm- Consequently, it is possible to eliminate the insufficiency of the output voltage Vout and the fall in luminance of the light source 310.
On the contrary, the voltage Vadj of the terminal ADJ preferably varies in a longer time than the control period Tpwm of the bypass switch circuit 450, during the fall of the output voltage Vout of the step-down converter 430. For example, the voltage Vadj of the terminal ADJ follows the output voltage Vout within a time scale greater than three or five times the control period Tpwm · [0078] FIGS. 10A and 10B are diagrams of principle representing examples of configuration of the voltage adjustment circuit 460. A voltage adjustment circuit 460a of FIG. 10A comprises a diode D21, a first resistor R ₂ i, a second resistor R22 and a capacitor C ₂ i- The circuit voltage adjustment 460a can be considered as a peak hold circuit 461, and the voltage Vadj of the terminal ADJ corresponds to the output voltage Vc ₂ i of the peak hold circuit 461.
A voltage adjustment circuit 460b in FIG. 10B is configured by a digital circuit. An A / D converter 462 converts the output detection voltage Vouts to a digital value S41. A peak detection circuit 463 is used to produce a peak detection signal S ₄₂ representing a peak of the digital value S ₄ j. A filter 464 receives the peak detection signal S ₄₂ and has a faster reactivity in the upward direction and a slower reactivity in the downward direction. A D / A converter 465 converts an output voltage S ₄ 3 from the filter 464 into an analog voltage Vadj · FIGS. 11A and 11B are diagrams of functional waveforms of the lighting circuit 400, when the curve distribution of light intensities is changed. FIG. 11A represents the operation when a distribution curve of the low light intensities PATI is transformed into a distribution curve of the high light intensities PAT2. At this point, the average value and the peak value of the output voltage Vout rise, and the waveform of the output voltage Vout changes. The voltage Vadj of the terminal ADJ rapidly follows the rise in the peak value of the output voltage Vout on a time scale shorter than a PWM modulation period Tpwm (preferably a time scale less than T _P wm / 2). Consequently, it is possible to avoid the fall in luminance of the light source 310, caused by the insufficiency of the output voltage Vout · FIG. 11B represents the operation when the distribution curve of the high light intensities PAT2 is transformed into a distribution curve for low light intensities PATI. At this point, the average value and the peak value of the output voltage Vqut fall, and the waveform of the output voltage Vout changes. The voltage Vadj of the terminal ADJ slowly follows the fall of the peak value of the output voltage Vout on a time scale greater than several times the modulation period PWM T _P wm (preferably a time scale greater than 3 x Tpwm) · Consequently, it is possible to avoid oscillation or instability of the system comprising the step-up converter 410 and the step-down converter 430.
[0082] Although the present invention has been described on the basis of the embodiments, the embodiments simply illustrate the principle and the application of the present invention. Various variations of modifications and configurations can be made to the embodiments, without departing from the inventive concept as defined in the claims.
(First modification)
In the embodiment described above, the voltage Vadj of the terminal ADJ is modified as a function of the output voltage Vout · However, the present invention is not limited to this. Switching models of the plurality of bypass switches 452 corresponding to each light intensity distribution curve are known. Therefore, a waveform of the output voltage Vout on each light intensity distribution curve can be estimated by calculation.
Figure 12 is a block diagram of the voltage adjustment circuit 460c according to a first modification. The voltage adjustment circuit 460c estimates a peak voltage value between the two ends of the light source 310 (namely a peak value of the output voltage Vout of the step-down converter 430) over a modulation period PWM, over the based on a model of the on / off states of the plurality of bypass switches 452_1 to 452_N, and regulates the voltage Vadj of the terminal ADJ on the basis of the estimated value. For example, an output voltage estimator 466 receives information S51 from the light intensity distribution curve and determines a peak value S52 of the output voltage Vout, within the PWM modulation period, based on S51 information. For example, a table showing a relationship between the light intensity distribution curve and the peak value can be kept in the output voltage estimator 466. A D / A converter 467 converts the peak value S52 into an analog signal and delivers it to the ADJ terminal. Functions of the output voltage estimator 466 and the D / A converter 467 can be implemented in the light distribution control device 470 or in the headlight ECU in common with the light distribution control device 470 .
According to this modification, the input voltage V _D c of the step-down converter 430 can be adjusted to an appropriate voltage level by regulation with anticipatory action, without detection of the output voltage Vout · [Second modification )
Figures 13A and 13B are block diagrams of lighting circuit 400b according to a second modification. The lighting circuit 400b drives a plurality (two channels here) of light sources 310_l and 310_2. The lighting circuit 400b comprises a plurality of step-down converters 430_l and 430_2 corresponding respectively to the plurality of light sources 310_l and 310_2. The plurality of step-down converters 430_l and 430_2 receives an output voltage Vdc of step-up converter 410. A voltage adjustment circuit 460b modifies the voltage Vadj of the terminal AD J according to the highest voltage among the output voltages Vouti and Vout2 of the plurality of step-down converters 430_l and 430_2.
FIG. 13B shows an example of configuration of the voltage adjustment circuit 460b. The configuration of the voltage adjustment circuit 460b is the same as that of FIG. 10A. A plurality of diodes D ₂ i corresponding to the plurality of channels has a shared cathode. The plurality of diodes D ₂ i operate as a maximum value circuit, and a voltage corresponding to the maximum voltage among the plurality of output detection voltages Voutsi and Vquts2 is produced at the cathode.

权利要求:
Claims (12)
[1" id="c-fr-0001]
1. Lighting circuit (400) configured to control a light source comprising a plurality of light emitting elements (312_1; 312_N) connected in series, the lighting circuit comprising:
a bypass switch circuit (450) which includes a plurality of bypass switches (452_1; 452_N), each of which is mounted in parallel with a corresponding light emitting element of the plurality of light emitting elements;
a step-up converter (410) which is configured to amplify a supply voltage to produce a stabilized direct voltage (Vdc) at a variable target voltage (Vdc (ref));
a step-down converter (430) which is configured to receive the DC voltage in order to supply a stabilized drive current (Ilamp) at a target current (Iref) to the light source (310), and which comprises a hysteresis regulator (480 ) according to a hysteresis control method, in which the hysteresis regulator (480) is configured to stabilize the drive current (Ilamp) between a maximum value (Iupper) and a minimum value (Ibottom) which are defined close to the target current, and to modify a difference between the maximum value and the minimum value, so that a switching frequency (f _sw ) of the step-down converter (430) tends towards a constant value; and a voltage setting circuit (460) which is configured to dynamically change the target voltage of the step-up converter, based on an output voltage of the step-down converter (430).
[2" id="c-fr-0002]
2. The lighting circuit (400) according to claim 1, in which the voltage adjustment circuit (460) is configured to modify the target voltage so that a difference between the target voltage of the step-up converter (410) and the output voltage of the step-down converter (430) does not exceed or tend towards a predetermined value.
[3" id="c-fr-0003]
3. Lighting circuit (400) according to claim 1 or 2, in which the voltage adjustment circuit (460) is configured to modify the target voltage more quickly when the output voltage (Vout) increases. step-down converter (430) only when the output voltage (Vout) of the step-down converter (430) drops.
[4" id="c-fr-0004]
4. Lighting circuit (400) according to any one of claims 1 to 3, in which the voltage regulation circuit (460) is configured to modify the target voltage in a shorter time than a control period of the bypass switch circuit (450), when the output voltage of the step-down converter (430) rises.
[5" id="c-fr-0005]
5. Lighting circuit (400) according to any one of claims 1 to 4, in which the voltage adjustment circuit (460) is configured to modify the target voltage in a time longer than a control period of the bypass switch circuit (450), when the output voltage of the step-down converter drops.
[6" id="c-fr-0006]
6. Lighting circuit (400) according to claim 5, in which the voltage regulation circuit (460) is configured to modify the target voltage (Vdc (ref)) in a time greater than three times the command period of the bypass switch circuit (450), when the output voltage of the step-down converter drops.
[7" id="c-fr-0007]
The lighting circuit (400) according to any of claims 1 to 6, wherein the voltage setting circuit (460) includes a peak hold circuit (461) which is configured to receive a sensing voltage. output corresponding to the output voltage of the step-down converter (430), and the target voltage corresponds to an output voltage of the peak hold circuit (461).
[8" id="c-fr-0008]
8. Lighting circuit (400) according to any one of claims 1 to 7, in which the voltage adjustment circuit (460) comprises:
a diode (D ₂ i) which is configured to receive an output detection voltage corresponding to the output voltage of the step-down converter, at an anode thereof;
a first resistor (R21) which is placed between a cathode of the diode and a ground;
a capacitor (C ₂ i) which has one end connected to ground; and a second resistor (R ₂₂ ) which is placed between the other end of the capacitor and the cathode of the diode, and in which the target voltage is fixed according to a voltage of the capacitor.
[9" id="c-fr-0009]
9. Lighting circuit (400) according to any one of claims 1 to 7, in which the voltage regulation circuit (460) comprises:
an A / D converter (462) which is configured to convert an output detection voltage corresponding to the output voltage of the step-down converter (430) to a digital value (S41);
a peak detection circuit (463) which is configured to produce a peak detection signal (S42) representing a peak of the digital value (S41);
a filter (464) which is configured to receive the peak detection signal and which has faster reactivity in an upward direction and slower reactivity in a downward direction; and a D / A converter (465) which is configured to convert an output signal of the filter into an analog voltage (Vadj), and wherein the target voltage is set according to the analog voltage.
[10" id="c-fr-0010]
10. Lighting circuit (400) according to any one of claims 1 to 6, further comprising:
a light distribution controller (470) which is configured to control the plurality of bypass switches according to a desired light intensity distribution curve, wherein the voltage adjusting circuit (460) is configured to adjust the target voltage based on a voltage between the two ends of the light source, estimated from the on / off states of the plurality of bypass switches.
[11" id="c-fr-0011]
11. Lighting circuit (400) according to any one of claims 1 to 10, in which the lighting circuit is configured to control a plurality of light sources (310_l; 310_2) and comprises a plurality of step-down converters (430_l ; 430_2) respectively corresponding to the plurality of light sources, and in which the voltage adjustment circuit (460b) is configured to modify the target voltage according to the highest voltage among the output voltages of the plurality of step-down converters .
[12" id="c-fr-0012]
12. Vehicle headlight (300) comprising:
a light source (310) comprising a plurality of light emitting elements (312_1; 312_N) connected in series; and the lighting circuit (400) according to any of claims 1 to 11, configured to control the light source.
1/10

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法律状态:
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2019-03-08| PLSC| Publication of the preliminary search report|Effective date: 20190308 |

2019-07-11| PLFP| Fee payment|Year of fee payment: 3 |

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优先权:

申请号 | 申请日 | 专利标题

JP2016164836|2016-08-25|

JP2016164836A|JP6830774B2|2016-08-25|2016-08-25|Lighting circuit and vehicle lighting|

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